Having a bd.tcl script in every IP is redundant.
adi_ip.tcl:
- add adi_init_bd_tcl - creates a blanch bd.tcl and a
parameters temporary_case_dependencies.mk when compiling an IP.
Its main purpose is to generate the bd.tcl, which will be included in
the IP's file-set.
- adi_auto_fill_bd_tcl will populate the empty bd.tcl based on the
top IP parameters and the presence of these parameters in
auto_set_param_list and auto_set_param_list_overwritable lists.
This task can not be performed by the first described procedure since
the file-set is not yet defined.
adi_xilinx_device_info_enc.tcl:
Split auto_set_param_list_overwritable from auto_set_param_list. As
the name states, some of the parameters are overwritable, this will help
when generating the bd.tcl script.
library.mk:
Include the temporary_case_dependencies.mk if it exists in the
IP root folder. The mentioned *.mk file contains non generic
dependencies for makefiles like targets to clean.
Common basic steps:
- Include/create infrastructure:
* Intel:
- require quartus::device package
- set_module_property VALIDATION_CALLBACK info_param_validate
* Xilinx
- add bd.tcl, containing init{} procedure. The init procedure will be
called when the IP will be instantiated into the block design.
- add to the xilinx_blockdiagram file group the bd.tcl and common_bd.tcl
- create GUI files
- add parameters in *_ip.tcl and *_hw.tcl (adi_add_auto_fpga_spec_params)
- add/propagate the info parameters through the IP verilog files
axi_clkgen
util_adxcvr
ad_ip_jesd204_tpl_adc
ad_ip_jesd204_tpl_dac
axi_ad5766
axi_ad6676
axi_ad9122
axi_ad9144
axi_ad9152
axi_ad9162
axi_ad9250
axi_ad9265
axi_ad9680
axi_ad9361
axi_ad9371
axi_adrv9009
axi_ad9739a
axi_ad9434
axi_ad9467
axi_ad9684
axi_ad9963
axi_ad9625
axi_ad9671
axi_hdmi_tx
axi_fmcadc5_sync
Xilinx:
When calling adi_auto_fpga_spec_params in the x_ip.tcl, parameters like
- FPGA_TECHNOLOGY
- FPGA_FAMILY
- SPEED_GRADE
- DEV_PACKAGE
- XCVR_TYPE
- FPGA_VOLTAGE
will be automatically detected and constrained to predefined pairs of values
from adi_xilinx_device_info_env.tcl
The parameters specified in the blobk diagram of the IP(bd.tcl), will be
automatically assign when the IP is added to a block design.
The "adi_auto_assign_device_spec $cellpath" is called in the init
hook (bd.tcl).
https://www.xilinx.com/products/technology/high-speed-serial.html
Intel:
Info parameters are set in the VALIDATION_CALLBACK according to
adi_intel_device_info_env.tcl
Fix the following warning:
WARNING: [Synth 8-2611] redeclaration of ANSI port up_es_reset is not allowed
Also make sure, that in all configurations, the register has a diver.
Add support for 8 bit resolution for the transport layer.
Fix parameter BITS_PER_SAMPLES propagation to all the internal modules, in
several cases this variable was hard coded to 16.
The axi_pulse_gen is a generic PWM generator, which can be configured
through an AXI Memory Mapped interface.
The current register map look like follows:
0x00 - VERSION
0x04 - ID
0x08 - SCRATCH
0x0C - IDENTIFICATION - 0x504c5347 which stands for 'PLSG' in ASCII
0x10 - CONFIGURATION - contains reset and load bits
0x14 - PULSE_PERIOD
0x18 - PULSE_WIDTH
Also update all the other modules, which instantiate the util_pulse_gen.
To prevent the case, when after an invalid configuration, the generated
output PWM signal is constant HIGH, change the counter to a
down-counter. In this way the pulse will be placed at the end of the
PWM period, and if the configured width value is higher than the
configured period the output signal will be constant LOW.
Write code to pipeline data path for better DSP utilization on the
color space conversion.
In the old method the addition operations were performed outside the
DSPs
The FIFO functions in 'first fall through' mode, adjust the fifo level
generation so it take into account the valid data which sits on the bus,
waiting for ready, too.
Current implementation does not supports updated versions of Vivado
e.g. 2017.4.1 or 2018.2.1
This fix ignores the update number from the version checking.
Registers from this component can fit in the 2k address range.
Since Vivado's minimal address range is 4k, use that instead.
This will allow placing the independent TPLs to base addresses
that mach the addresses from the monolithic blocks ensuring no software
intervention.
The DMAC has the requirement that the length of the transfer is aligned to
the widest interface width. E.g. if the widest interface is 256 bit or 32
bytes the length of the transfer needs to be a multiple of 32.
This restriction can be relaxed for the memory mapped interfaces. This is
done by partially ignoring data of a beat from/to the MM interface.
For write access the stb bits are used to mask out bytes that do not
contain valid data.
For read access a full beat is read but part of the data is discarded. This
works fine as long as the read access is side effect free. I.e. this method
should not be used to access data from memory mapped peripherals like a
FIFO.
This means that for example the length alignment requirement of a DMA
configured for a 64-bit memory and a 16-bit streaming interface is now only
2 bytes instead of 8 bytes as before.
Note that the address alignment requirement is not affected by this. The
address still needs to be aligned to the width of the MM interface that it
belongs to.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
FPGAs support different widths for the read and write port of the block
SRAM cells. The DMAC can make use of this feature when the source and
destination interface have a different width to up-size/down-size the data
bus.
Using memory cells with asymmetric port width consumes the same amount of
SRAM cells, but allows to bypass the re-size blocks inside the DMAC that
are otherwise used for up- and down-sizing. This reduces overall resource
usage and can improve timing.
If the ratio between the destination and source port is too larger to be
handled by SRAM alone the SRAM block will be configured to do partial up-
or down-sizing and a resize block will be inserted to take care of the
remaining up-/down-sizing. E.g. if a 256-bit interface is connected to a
32-bit interface the SRAM will be used to do an initial resizing of 256 bit
to 64 bit and a resize block will be used to do the remaining resizing from
64 bit to 32 bit.
Currently this feature is disabled for Intel FPGAs since Quartus does not
properly infer a block RAM with different read and write port widths from
the current ad_asym_mem module. Once that has been resolved support for
asymmetric memories can also be enabled in the DMAC.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
The handling of the src_data_valid_bytes signal and its related signal is
tightly coupled to the behavior of the resize_src module. The code that
handles it makes assumptions about the internal behavior of the resize_src
module.
Move the handling of the src_data_valid_bytes signal when upsizing the data
bus into the resize_src module so that all the code that is related is in
the same place and the code outside of the module does not have to care
about the internals.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
The DMA_LENGTH_ALIGN LSBs of all length For the most part the tools are
able to deduce this using constant propagation.
But this propagation does not work across the asynchronous meta data FIFO
in the burst memory module.
Add a DMA_LENGTH_ALIGN parameter to the burst_memory module which is used
to explicitly keep the LSBs of length registers on the destination side
fixed at 1'b1. This reduces resource use and improves timing by allowing
better constant propagation and unused logic elimination.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
This simplifies the burst length in the response manager significantly
while not costing much extra resources in the burst memory.
This change will also enable other future improvements.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
One of the major features of the DMAC is being able to handle non matching
interface widths for the destination and source side.
Currently the test benches only support the case where the width for the
source and the destination side are the same. Extend them so that it is
possible to also test and verify setups where the width is not the same.
To accomplish this each byte memory location is treated as if it contained
the lower 8 bytes of its address. And then the written/read data is
compared to the expected data based on that.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
On Arria10 there are 6 transceivers in a single bank. If more than 6
transceivers are used these will end up in multiple banks.
The ATX PLL can directly connect to the transceivers in the same bank
through the 1x clock network. To connect to transceivers in another bank it
has to go through a master clock generation block (MCGB) and the xN clock
network.
Add support for instantiating the MCGB if more than 6 lanes are used. In
this case the first 6 transceivers will still have a direct connection to
the PLL while all other transceivers will be clocked by the MCGB.
Note that this requires that the first 6 transceivers are all in the same
bank.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
All projects have been updated to use the new pack/unpack infrastructure.
The old util_cpack and util_upack cores are now unused an can be removed.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
The util_cpack2 core is similar to the util_upack core. It packs, or
interleaves, a data from multiple ports into a single data. Ports can
optionally be enabled or disabled.
On the input side the cpack2 core uses a multi-port FIFO interface. There
is a single data write signal (fifo_wr_en) for all ports. But each port can
be individually enabled or disabled using the enable signals.
On the output side the cpack2 core uses a single port FIFO interface. When
data is available on the output interface the data write signal
(packed_fifo_wr_en). Data on the packed_fifo_wr_data signal is only valid
when packed_fifo_wr_en is asserted. At other times the content is
undefined. The cpack2 core offers no back-pressure. If data is not consumed
when it is made available it will be lost.
Data from the input ports is accumulated inside the cpack2 core and if
enough data is available to produce a full output vector the data is
forwarded.
This core is build using the common pack infrastructure. The core that is
specific to the cpack2 core is mainly only responsible for generating the
control signals for the external interfaces.
The core is accompanied by a test bench that verifies correct behavior for
all possible combinations of enable masks.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
The util_upack2 core is similar to the util_upack core. It unpacks, or
deinterleaves, a data stream onto multiple ports.
The upack2 core uses a streaming AXI interface for its data source instead
of a FIFO interface like the upack core uses.
On the output side the upack2 core uses a multi-port FIFO interface. There
is a single data request signal (fifo_rd_en) for all ports. But each port
can be individually enabled or disabled using the enable signals.
This modified architecture allows the upack2 core to better generate the
valid and underflow control signals to indicate whether data is available
in a response to a data request.
If fifo_rd_en is asserted and data is available the fifo_rd_valid signal
are asserted in the following clock cycle. The enabled fifo_rd_data ports
will be contain valid data during the same clock cycle as fifo_rd_valid is
asserted. During other clock cycles the output data is undefined. On
disabled ports the data is always undefined.
If no data is available instead the fifo_rd_underflow signal is asserted in
the following clock cycle and the output of all fifo_rd_data ports is
undefined.
This core is build using the common pack infrastructure. The core that is
specific to the upack2 core is mainly only responsible for generating the
control signals for the external interfaces.
The core is accompanied by a test bench that verifies correct behavior for
all possible combinations of enable masks.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
Pack and unpack operations are very similar in structure as such it makes
sense for pack and unpack core to share a common infrastructure.
The infrastructure introduced in this patch is based on a routing network
which can implement the pack and unpack operations and grows with a
complexity of N * log(N) where N is the number of channels times the number
of samples per channel that are process in parallel.
The network is constructed from a set of similar stages composed of either
2x2 or 4x4 switches. Control signals for the switches are fully registered
and are generated one cycle in advance.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
Add support for Vivado's simulator. By default the run script is using
the Icarus simulator.
If the user want to switch to another simulator, it can be explicitly
specify the required simulator tool in the SIMULATOR variable.
Currently, beside Icarus, Modelsim (SIMULATOR="modelsim") and Vivado's
xsim (SIMULATOR="xsim") is supported.
For consistent simulation behavior it is recommended to annotate all source
files with a timescale. Add it to those where it is currently missing.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
By default inferred output reset signals have an active low polarity. The
axi_ad9361 rst output signal is active high though. Currently when
connecting it to a input reset with active high polarity will generate an
error in IPI.
Fix this by explicitly marking the polarity of the rst signal as active
high.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
Replace the open-coded instances of a perfect shuffle in the DAC framer with
the new helper module.
Using the helper module gives well defined semantics and hopefully makes
the code easier to understand.
There are no changes in behavior.
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
The perfect shuffle is a common operation in data processing. Add a shared
module that implements this operation.
Having this in a shared module rather than open-coding every instance makes
sure that there are clear and well defined semantics associated with the
operation that are the same each time. This should ease review, maintenance and
understanding of the code.
The perfect shuffle splits the input vector into NUM_GROUPS groups and then
each group in WORDS_PER_GROUP. The output vector consists of
WORDS_PER_GROUP groups and each group has NUM_GROUPS words. The data is
remapped, so that the i-th word of the j-th word in the output vector is
the j-th word of the i-th group of the input vector.
The inverse operation of the perfect shuffle is the perfect shuffle with
both parameters swapped.
I.e. [perfect_suffle B A [perfect_shuffle A B data]] == data
Examples:
NUM_GROUPS = 2, WORDS_PER_GROUP = 4
[A B C D a b c d] => [A a B b C c D d]
NUM_GROUPS = 4, WORDS_PER_GROUP = 2
[A a B b C c D d] => [A B C D a b c d]
NUM_GROUPS = 3, WORDS_PER_GROUP = 2
[A B a b 1 2] => [A a 1 B b 2]
Signed-off-by: Lars-Peter Clausen <lars@metafoo.de>
The write logic (DMA side) has to be independent from the read logic (DAC side).
In general the FIFO is always ready for the DMA, and every DMA transaction will
interrupt the read-back process, and the module will stop sending data,
until the initialization is finished.
Bringing back the write address tot he DMA clock domain is totally
redundant, so delete it.
Expose the TX configurable driver ports, more specifically the
TX_DIFFCTRL, TX_POSTCURSORE and TX_PRECURSORE for software. This
provides a soft tunning capability of the transmit side of the
transceivers, in cases where the insertion loss of the channel is too
high or low, comparing to the default value supported by the default
configuration of the GTs.
You can find information about these configuration ports under the
section called 'TX Configurable Driver' in the GT transceivers user
guide. (UG476, UG576)
This commit does not contain any functional modification.
Because the wizard generates the attributes in binary, we should use
binary mode too, so we can compare different configurations more easily.
If the req_valid asserts faster than the ID gets synchronized over we
assert the xfer request without being ready to accept data.
This can lead to overflow assertion when using a FIFO like interface.
Data mover/ src axis changes
Request rewind ID if TLAST received during non-last burst
Consume (ignore) descriptors until last segment received
Block descriptors towards destination until last segment received
Request generator changes
Rewind the burst ID if rewind request received
Consume (ignore) descriptors until last segment received
If TLAST happened on last segment replay next transfer (in progress or
completed) with the adjusted ID
Create completion requests for ignored segments
Response generator changes
Track requests
Complete segments which got ignored
Edward Kigwana
AndreiGrozav
Adrian Costina
Istvan Csomortani
sarpadi
Sergiu.Arpadi
Laszlo Nagy
Lars-Peter Clausen